MICRF001BN Просмотр технического описания (PDF) - Micrel

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MICRF001BN

QwikRadio Receiver/Data Demodulator

Micrel 

MICRF001

QwikRadio tm

Micrel

External Control Signals and Mode Selection

For applications where the transmit frequency is accurately

set for other reasons (e.g., applications where a SAW

transmitter is used for its mechanical stability), the user may

choose to configure the MICRF001 as a standard

superheterodyne receiver (FIXED mode), mitigating the

aforementioned problem of a competing close-in signal. This

can be accomplished by tying SWEN to ground. Doing so

forces the on-chip LO frequency to a fixed value. In such a

case, the ceramic resonator would be replaced with a crystal.

Generally, however, the MICRF001 can be operated with a

ceramic resonator adequately, no matter whether the

transmitter is LC or SAW based.

The third approach is attractive for further lowering system

cost if an accurate reference signal exists elsewhere in the

system (e.g., a reference clock from a crystal or ceramic

resonator-based microprocessor), and flexibility exists in the

choice of system transmit frequency. An externally applied

signal should be AC-coupled, and resistively-divided down

(or otherwise limited) to approximately 0.5Vpp. The specific

reference frequency required is related to the system

transmit frequency, and the operating mode of the device as

set by the SWEN control pin. See “Application Note 22,

MICRF001 Theory of Operation” for a discussion of

frequency selection and accuracy requirements.

I/O Pin Interface Circuitry

Slicing Level and the CTH Capacitor

Extraction of the DC value of the demodulated signal for

purposes of logic-level data slicing is accomplished by

external capacitor CTH and the on-chip switched-cap

“resistor” RSC, indicated in the block diagram. The effective

resistance of RSC varies in the same way as the

Demodulator filter bandwidth, in four binary steps, from

approximately 1600kΩ to 200kΩ. Once the filter bandwidth

is selected, this “resistance” is determined; then the value of

capacitor CTH is easily calculated, once the slicing level

time-constant is chosen. Values vary somewhat with

decoder type, but typical Slicing Level time constants range

5-50msec. Optimization of the CTH value is required to

maximize range, as discussed in “Application Note 22,

MICRF001 Theory of Operation”, section 6.4.

Interface circuitry for the various I/O pins of the MICRF001 is

shown in Figures 1 through 6. Specific information regarding

each of these circuits is discussed in the following sub-

paragraphs. Not shown are ESD protection diodes which

are applied to all input pins.

1. ANT Pin

The ANT pin is internally AC-coupled via a 3pF capacitor, to

an RF N-channel MOSFET, as shown in Figure 1.

Impedance on this pin to VSS is quite high at low

frequencies, and decreases as frequency increases. In the

UHF frequency range, the device input can be modeled as

6.3kΩ in parallel with 2pF (pin capacitance) shunt to VSSRF.

AGC Function and the CAGC Capacitor

The signal path has automatic gain control (AGC) to increase

input dynamic range. An external capacitor, CAGC, must be

applied to set the AGC attack and decay time-constants.

With the addition of only a capacitor, the ratio of decay-to-

attack time-constant is fixed at 10:1 (i.e., the attack time

constant is 1/10th the decay time constant), and this ratio

cannot be changed by the user. However, the attack time

constant is selectable by the user through the value of

capacitor CAGC. By adding resistance from the CAGC pin

to VDDBB or VSSBB in parallel with the CAGC capacitor, the

ratio of decay-to-attack time-constant may be varied. See

“Application Note 22, MICRF001 Theory of Operation”.

2. CTH Pin

Figure 1 ANT Pin

Reference Oscillator (REFOSC) and External Timing

Element

All timing and tuning operations on the MICRF001 are

derived from the REFOSC function. This function is a single-

pin Colpitts-type oscillator. The user may handle this pin in

one of three possible ways:

(1) connect a ceramic resonator, or

(2) connect a crystal, or

(3) drive this pin with an external timing signal.

Figure 2 illustrates the CTH pin interface circuit. CTH pin is

driven from a P-channel MOSFET source-follower biased

with approximately 20µA of bias current. Transmission gates

TG1 and TG2 isolate the 3.3pF capacitor. Internal control

signals PHI1/PHI2 are related in a manner such that the

impedance across the transmission gates looks like a

“resistance”. The DC potential on the CTH pin is

approximately 2.2V, fundamentally determined by the Vgs of

the two P-channel MOSFET source-followers shown.

June 1998

6

MICRF001

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