AD9767-EB Просмотр технического описания (PDF) - Analog Devices

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AD9767-EB

14-Bit, 125 MSPS Dual TxDAC+® D/A Converter

Analog Devices 

AD9767

IOUTFS and RLOAD can be selected as long as the positive compli-

ance range is adhered to. One additional consideration in this

mode is the integral nonlinearity (INL) as discussed in the

Analog Output section of this data sheet. For optimum INL

performance, the single-ended, buffered voltage output configu-

ration is suggested.

AD9767

IOUTA

IOUTB

IOUTFS = 20mA

25⍀

50⍀

VOUTA = 0 TO +0.5V

50⍀

Figure 36. 0 V to 0.5 V Unbuffered Voltage Output

SINGLE-ENDED, BUFFERED VOLTAGE OUTPUT

CONFIGURATION

Figure 37 shows a buffered single-ended output configuration

in which the op amp U1 performs an I-V conversion on the

AD9767 output current. U1 maintains IOUTA (or IOUTB) at a

virtual ground, thus minimizing the nonlinear output impedance

effect on the DAC’s INL performance as discussed in the

Analog Output section. Although this single-ended configura-

tion typically provides the best dc linearity performance, its ac

distortion performance at higher DAC update rates may be

limited by U1’s slewing capabilities. U1 provides a negative

unipolar output voltage and its full-scale output voltage is sim-

ply the product of RFB and IOUTFS. The full-scale output should

be set within U1’s voltage output swing capabilities by scaling

IOUTFS and/or RFB. An improvement in ac distortion perfor-

mance may result with a reduced IOUTFS since the signal current

U1 will be required to sink will be subsequently reduced.

AD9767

IOUTA

IOUTB

IOUTFS = 10mA

200⍀

COPT

RFB

200⍀

U1

VOUT = IOUTFS ؋ RFB

Figure 37. Unipolar Buffered Voltage Output

POWER AND GROUNDING CONSIDERATIONS, POWER

SUPPLY REJECTION

Many applications seek high speed and high performance under

less than ideal operating conditions. In these application cir-

cuits, the implementation and construction of the printed circuit

board is as important as the circuit design. Proper RF tech-

niques must be used for device selection, placement and rout-

ing, as well as power supply bypassing and grounding to ensure

optimum performance. Figures 43 to 50 illustrate the recom-

mended printed circuit board ground, power and signal plane

layouts which are implemented on the AD9767 evaluation board.

One factor that can measurably affect system performance is the

ability of the DAC output to reject dc variations or ac noise

superimposed on the analog or digital dc power distribution.

This is referred to as the Power Supply Rejection Ratio. For dc

variations of the power supply, the resulting performance of the

DAC directly corresponds to a gain error associated with the

DAC’s full-scale current, IOUTFS. AC noise on the dc supplies is

common in applications where the power distribution is gener-

ated by a switching power supply. Typically, switching power

supply noise will occur over the spectrum from tens of kHz to

several MHz. The PSRR vs. frequency of the AD9767 AVDD

supply over this frequency range is shown in Figure 38.

90

85

80

75

70

0.2 0.3 0.4 0.5 0.6 0.7 0.8 0.9 1.0 1.1

FREQUENCY – MHz

Figure 38. Power Supply Rejection Ratio of AD9767

Note that the units in Figure 38 are given in units of (amps out/

volts in). Noise on the analog power supply has the effect of

modulating the internal current sources, and therefore the out-

put current. The voltage noise on AVDD, therefore, will be

added in a nonlinear manner to the desired IOUT. PSRR is very

code-dependent thus producing mixing effects which can modu-

late low frequency power supply noise to higher frequencies.

Worst case PSRR for either one of the differential DAC outputs

will occur when the full-scale current is directed towards that

output. As a result, the PSRR measurement in Figure 38 repre-

sents a worst case condition in which the digital inputs remain

static and the full-scale output current of 20 mA is directed to

the DAC output being measured.

An example serves to illustrate the effect of supply noise on the

analog supply. Suppose a switching regulator with a switching

frequency of 250 kHz produces 10 mV of noise and, for simplic-

ity sake (i.e., ignore harmonics), all of this noise is concentrated

at 250 kHz. To calculate how much of this undesired noise will

appear as current noise superimposed on the DAC’s full-scale

current, IOUTFS, one must determine the PSRR in dB using

Figure 38 at 250 kHz. To calculate the PSRR for a given RLOAD,

such that the units of PSRR are converted from A/V to V/V,

adjust the curve in Figure 38 by the scaling factor 20 × Log

(RLOAD ). For instance, if RLOAD is 50 Ω, the PSRR is reduced

by 34 dB (i.e., PSRR of the DAC at 250 kHz, which is 85 dB in

Figure 38, becomes 51 dB VOUT/VIN).

REV. B

–15–

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